CROSS-REFERENCE TO RELATED APPLICATION

This application is a continuation application of International Application No. PCT/JP2021/027606, filed Jul. 26, 2021, the disclosure of which is incorporated herein by reference in its entirety. Further, this application claims priority from Japanese Patent Application No. 2020-130627 filed on Jul. 31, 2020, the disclosure of which is incorporated herein by reference in its entirety.

BACKGROUND
1. Technical Field

The technique of the present disclosure relates to an optical scanning device, a method of driving the optical scanning device, and an image drawing system.

2. Description of the Related Art

A micromirror device (also referred to as a microscanner) is known as one of micro electro mechanical systems (MEMS) devices manufactured using the silicon (Si) nanofabrication technique. Since an optical scanning device comprising the micromirror device is small and has low power consumption, it is expected to have a range of applications in an image drawing system such as a laser display or a laser projector.

In the micromirror device, a mirror portion is formed to be swingable around a first axis and a second axis that are orthogonal to each other, and two-dimensional scan with light reflected by the mirror portion is made by allowing the mirror portion to swing around each axis. In addition, there is known a micromirror device capable of performing Lissajous scanning with light by allowing the mirror portion to resonate around each axis.

In such a micromirror device, in order to accurately control a deflection angle of the mirror portion, it is known to provide an angle detection sensor that outputs a signal corresponding to an angle of the mirror portion (for example, see JP2019-082634A and JP2018-063228A).

JP2019-082634A discloses “obtaining an amplitude of rotation of a mirror portion based on an output signal of a detection signal acquisition unit”. Specifically, JP2019-082634A discloses “obtaining a peak to peak (P-P) value of a change of a signal voltage corresponding to rotation of the mirror portion, and obtaining an amplitude of rotation of the mirror portion based on data indicating a relationship between the signal voltage and the amplitude of rotation of the mirror portion”. The amplitude of rotation of the mirror portion corresponds to the maximum value of the deflection angle (hereinafter, the maximum deflection angle).

JP2018-063228A discloses “acquiring a swing angle of a MEMS mirror based on an amount of change in an angle of the MEMS mirror with respect to a resonance direction in a case where the MEMS mirror is driven at a resonance frequency”.

SUMMARY

JP2019-082634A and JP2018-063228A disclose that a first angle detection sensor that detects an angle of the mirror portion around a first axis and a second angle detection sensor that detects an angle of the mirror portion around a second axis are provided. However, in a case where the mirror portion swings around the first axis and the second axis simultaneously, a vibration component caused by the swing of the mirror portion around the second axis is superimposed on an output signal of the first angle detection sensor. A vibration component caused by the swing of the mirror portion around the first axis is superimposed on the output signal of the second angle detection sensor. As described above, in a biaxial drive type micromirror device, there is a problem that vibration of an axis different from an axis to be detected is superimposed as noise on an output signal of an angle detection sensor. Hereinafter, this noise is referred to as a vibration noise.

In order to keep the maximum deflection angle of the mirror portion constant, it is necessary to accurately detect the amplitude of the output signal of the angle detection sensor. In addition, in a case where the mirror portion is resonantly driven, it is necessary to accurately detect a phase of the output signal of the angle detection sensor in order to maintain the resonance state of the swing of the mirror portion.

However, in a case where a vibration noise is superimposed on the output signal of the angle detection sensor, the amplitude and phase of the output signal of the angle detection sensor cannot be accurately detected, and it is difficult to accurately control the swing of the mirror portion.

An object of the technique of the present disclosure is to provide an optical scanning device, a method of driving the optical scanning device, and an image drawing system which can accurately control swing of a mirror portion.

According to the technique of the present disclosure, it is possible to provide an optical scanning device, a method of driving the optical scanning device, and an image drawing system which can accurately control a deflection angle of a mirror portion.

In order to achieve the above object, according to the present disclosure, there is provided an optical scanning device comprising: a mirror portion having a reflecting surface for reflecting incident light; a first actuator that allows the mirror portion to swing around a first axis located in a plane including the reflecting surface of the mirror portion in a stationary state; a second actuator that allows the mirror portion to swing around a second axis which is located in the plane including the reflecting surface of the mirror portion in the stationary state and is orthogonal to the first axis; a pair of first angle detection sensors that output a signal corresponding to an angle of the mirror portion around the first axis, the pair of first angle detection sensors being disposed at positions facing each other across the first axis or the second axis; and at least one processor, in which the processor generates a first angle detection signal representing the angle of the mirror portion around the first axis by adding or subtracting a pair of first output signals output from the pair of first angle detection sensors.

It is preferable that the processor adjusts an amplitude level of at least one of the pair of first output signals to match amplitudes of vibration noises respectively included in the pair of first output signals with each other, and then adds or subtracts the pair of first output signals.

It is preferable that the pair of first angle detection sensors are disposed at the positions facing each other across the first axis, and that the processor generates the first angle detection signal by subtracting one of the pair of first output signals whose amplitude level has been adjusted from the other.

It is preferable that the pair of first angle detection sensors are disposed at the positions facing each other across the second axis, and that the processor generates the first angle detection signal by adding the pair of first output signals whose amplitude level has been adjusted.

It is preferable that the processor includes a first driving signal generation unit that generates a first driving signal applied to the first actuator, and feeds back the first angle detection signal to the first driving signal generation unit.

It is preferable that the first driving signal generation unit is a drive circuit having a phase synchronization circuit.

It is preferable that the first driving signal is a sinusoidal wave.

It is preferable that the first angle detection sensor is a piezoelectric element.

It is preferable that the optical scanning device further comprises: a pair of second angle detection sensors that output a signal corresponding to an angle of the mirror portion around the second axis, the pair of second angle detection sensors being disposed at positions facing each other across the first axis or the second axis, and that the processor generates a second angle detection signal representing the angle of the mirror portion around the second axis by adjusting an amplitude level of at least one of a pair of second output signals output from the pair of second angle detection sensors and adding or subtracting the pair of second output signals whose amplitude level has been adjusted.

It is preferable that the processor adjusts the amplitude level of at least one of the pair of second output signals to match amplitudes of vibration noises respectively included in the pair of second output signals with each other, and then adds or subtracts the pair of second output signals.

It is preferable that the pair of second angle detection sensors are disposed at the positions facing each other across the second axis, and that the processor generates the second angle detection signal by subtracting one of the pair of second output signals whose amplitude level has been adjusted from the other.

It is preferable that the pair of second angle detection sensors are disposed at the positions facing each other across the first axis, and that the processor generates the second angle detection signal by adding the pair of second output signals whose amplitude level has been adjusted.

It is preferable that the processor includes a second driving signal generation unit that generates a second driving signal applied to the second actuator, and feeds back the second angle detection signal to the second driving signal generation unit.

It is preferable that the second driving signal generation unit is a drive circuit having a phase synchronization circuit.

It is preferable that the second driving signal is a sinusoidal wave.

It is preferable that the second angle detection sensor is a piezoelectric element.

According to the present disclosure, there is provided an image drawing system comprising: the optical scanning device according to any one of the aspects; and a light source that irradiates the mirror portion with light, in which the processor controls a light irradiation timing of the light source based on the first angle detection signal and the second angle detection signal.

According to the present disclosure, there is provided a method of driving an optical scanning device including a mirror portion having a reflecting surface for reflecting incident light, a first actuator that allows the mirror portion to swing around a first axis located in a plane including the reflecting surface of the mirror portion in a stationary state, a second actuator that allows the mirror portion to swing around a second axis which is located in the plane including the reflecting surface of the mirror portion in the stationary state and is orthogonal to the first axis, and a pair of first angle detection sensors that output a signal corresponding to an angle of the mirror portion around the first axis, the pair of first angle detection sensors being disposed at positions facing each other across the first axis or the second axis, the method comprising: generating a first angle detection signal representing the angle of the mirror portion around the first axis by adding or subtracting a pair of first output signals output from the pair of first angle detection sensors.

BRIEF DESCRIPTION OF THE DRAWINGS

Exemplary embodiments according to the technique of the present disclosure will be described in detail based on the following figures, wherein:

FIG. 1 is a schematic view of an optical scanning device,

FIG. 2 is an external perspective view of a micromirror device,

FIG. 3 is a plan view of the micromirror device as viewed from a light incident side,

FIG. 4 is a cross-sectional view taken along the line A-A of FIG. 3,

FIG. 5 is a cross-sectional view taken along the line B-B of FIG. 3,

FIG. 6 is a cross-sectional view taken along the line C-C of FIG. 3,

FIG. 7 is a diagram showing an example in which a first actuator is driven,

FIG. 8 is a diagram showing an example in which a second actuator is driven,

FIGS. 9A and 9B are diagrams showing examples of a first driving signal and a second driving signal,

FIG. 10 is a block diagram showing an example of a configuration of a driving controller,

FIG. 11 is a diagram showing an example of signals output from a pair of first angle detection sensors,

FIG. 12 is a diagram showing an example of signals output from a pair of second angle detection sensors,

FIG. 13 is a circuit diagram showing a configuration of a first signal processing unit,

FIG. 14 is a diagram showing filter characteristics of a first BPF circuit and a second BPF circuit included in a gain adjustment circuit of the first signal processing unit,

FIG. 15 is a diagram showing an example of first signal processing,

FIG. 16 is a circuit diagram showing a configuration of a second signal processing unit,

FIG. 17 is a diagram showing filter characteristics of a first BPF circuit and a second BPF circuit included in a gain adjustment circuit of the second signal processing unit,

FIG. 18 is a diagram showing an example of second signal processing,

FIG. 19 is a block diagram showing an example of a configuration of a first driving signal generation unit,

FIG. 20 is a block diagram showing an example of a configuration of a second driving signal generation unit,

FIG. 21 is a diagram illustrating a generation process of a first zero cross pulse,

FIG. 22 is a diagram illustrating a generation process of a second zero cross pulse,

FIG. 23 is a plan view of a micromirror device according to a second embodiment,

FIG. 24 is a diagram showing an example of signals output from a pair of first angle detection sensors according to the second embodiment,

FIG. 25 is a diagram showing an example of signals output from a pair of second angle detection sensors according to the second embodiment,

FIG. 26 is a block diagram showing a configuration of a first driving signal generation unit according to the second embodiment,

FIG. 27 is a diagram showing an example of first signal processing according to the second embodiment,

FIG. 28 is a block diagram showing a configuration of a second driving signal generation unit according to the second embodiment,

FIG. 29 is a diagram showing an example of second signal processing according to the second embodiment, and

FIG. 30 is a diagram showing an example of gain and phase characteristics of a band pass filter circuit.

DETAILED DESCRIPTION

An example of an embodiment relating to the technique of the present disclosure will be described with reference to the accompanying drawings.

First Embodiment

FIG. 1 schematically shows an image drawing system 10 according to an embodiment. The image drawing system 10 includes an optical scanning device 2 and a light source 3. The optical scanning device 2 includes a micromirror device (hereinafter, referred to as micromirror device (MMD)) 4 and a driving controller 5. The driving controller 5 is an example of a “processor” according to the technique of the present disclosure.

The image drawing system 10 draws an image by reflecting a light beam L emitted from the light source 3 by the MMD 4 and optically scanning a surface to be scanned 6 with the reflected light beam under the control of the driving controller 5. The surface to be scanned 6 is, for example, a screen.

The image drawing system 10 is applied to, for example, a Lissajous scanning type laser display. Specifically, the image drawing system 10 can be applied to a laser scanning display such as augmented reality (AR) glass or virtual reality (VR) glass.

The MMD 4 is a piezoelectric biaxial drive type micromirror device capable of allowing a mirror portion 20 (see FIG. 2) to swing around a first axis a₁and a second axis a₂orthogonal to the first axis a₁. Hereinafter, the direction parallel to the second axis a₂is referred to as an X direction, the direction parallel to the first axis a₁is a Y direction, and the direction orthogonal to the first axis a₁and the second axis a₂is referred to as a Z direction.

The light source 3 is a laser device that emits, for example, laser light as the light beam L. It is preferable that the light source 3 emits the light beam L perpendicularly to a reflecting surface 20A (see FIG. 2) included in the mirror portion 20 in a state where the mirror portion 20 of the MMD 4 is stationary. In a case where the light beam L is emitted from the light source 3 perpendicularly to the reflecting surface 20A, the light source 3 may become an obstacle in scanning the surface to be scanned 6 the light beam L for drawing. Therefore, it is preferable that the light beam L emitted from the light source 3 is controlled by an optical system to be emitted perpendicularly to the reflecting surface 20A. The optical system may include a lens or may not include a lens. An angle at which the light beam L emitted from the light source 3 is applied to the reflecting surface 20A is not limited to the perpendicular direction, and the light beam L may be emitted obliquely to the reflecting surface 20A.

The driving controller 5 outputs a driving signal to the light source 3 and the MMD 4 based on optical scanning information. The light source 3 generates the light beam L based on the input driving signal and emits the light beam L to the MMD 4. The MMD 4 allows the mirror portion 20 to swing around the first axis a₁and the second axis a₂based on the input driving signal.

As will be described in detail below, the driving controller 5 allows the mirror portion 20 to resonate around the first axis a₁and the second axis a₂, so that the surface to be scanned 6 is scanned with the light beam L reflected by the mirror portion 20 such that a Lissajous waveform is drawn. This optical scanning method is called a Lissajous scanning method.

Next, an example of the MMD 4 will be described with reference to FIGS. 2 to 6. FIG. 2 is an external perspective view of the MMD 4. FIG. 3 is a plan view of the MMD 4 as viewed from the light incident side. FIG. 4 is a cross-sectional view taken along the line A-A in FIG. 3. FIG. 5 is a cross-sectional view taken along the line B-B of FIG. 3. FIG. 6 is a cross-sectional view taken along the line C-C of FIG. 3.

As shown in FIGS. 2 and 3, the MMD 4 includes a mirror portion 20, a first support portion 21, a first movable frame 22, a second support portion 23, a second movable frame 24, a connecting portion 25, and a fixed frame 26. The MMD 4 is a so-called MEMS scanner.

The mirror portion 20 has a reflecting surface 20A for reflecting incident light. The reflecting surface 20A is provided on one surface of the mirror portion 20, and is formed of a metal thin film such as gold (Au), aluminum (Al), silver (Ag), or an alloy of silver. The shape of the reflecting surface 20A is, for example, circular with the intersection of the first axis a₁and the second axis a₂as the center.

The first axis a₁and the second axis a₂exist in a plane including the reflecting surface 20A in a case where the mirror portion 20 is stationary. The planar shape of the MMD 4 is rectangular, line-symmetrical with respect to the first axis a₁, and line-symmetrical with respect to the second axis a₂.

The first support portions 21 are disposed on an outside of the mirror portion 20 at positions facing each other across the second axis a₂. The first support portions 21 are connected to the mirror portion 20 on the first axis a₁, and swingably support the mirror portion 20 around the first axis a₁. In the present embodiment, the first support portion 21 is a torsion bar stretched along the first axis a₁.

The first movable frame 22 is a rectangular frame that surrounds the mirror portion 20 and is connected to the mirror portion 20 on the first axis a₁via the first support portion 21. Piezoelectric elements 30 are formed on the first movable frame 22 at positions facing each other across the first axis a₁. In this way, a pair of first actuators 31 are configured by forming two piezoelectric elements 30 on the first movable frame 22.

The pair of first actuators 31 are disposed at positions facing each other across the first axis a₁. The first actuators 31 allow the mirror portion 20 to swing around the first axis a₁by applying rotational torque around the first axis a₁to the mirror portion 20.

The second support portions 23 are disposed on an outside of the first movable frame 22 at positions facing each other across the first axis a₁. The second support portions 23 are connected to the first movable frame 22 on the second axis a₂, and swingably support the first movable frame 22 and the mirror portion 20 around the second axis a₂. In the present embodiment, the second support portion 23 is a torsion bar stretched along the second axis a₂.

The second movable frame 24 is a rectangular frame that surrounds the first movable frame 22 and is connected to the first movable frame 22 on the second axis a₂via the second support portion 23. The piezoelectric elements 30 are formed on the second movable frame 24 at positions facing each other across the second axis a₂. In this way, a pair of second actuators 32 are configured by forming two piezoelectric elements 30 on the second movable frame 24.

The pair of second actuators 32 are disposed at positions facing each other across the second axis a₂. The second actuators 32 allow the mirror portion 20 to swing around the second axis a₂by applying rotational torque around the second axis a₂to the mirror portion 20 and the first movable frame 22.

The connecting portions 25 are disposed on an outside of the second movable frame 24 at positions facing each other across the first axis a₁. The connecting portions 25 are connected to the second movable frame 24 on the second axis a₂.

The fixed frame 26 is a rectangular frame that surrounds the second movable frame 24 and is connected to the second movable frame 24 on the second axis a₂via the connecting portion 25.

The first movable frame 22 is provided with a pair of first angle detection sensors 11A and 11B at positions facing each other across the first axis a₁in the vicinity of the first support portion 21. Each of the pair of first angle detection sensors 11A and 11B is composed of a piezoelectric element. Each of the first angle detection sensors 11A and 11B converts a force applied by deformation of the first support portion 21 accompanying the rotation of the mirror portion 20 around the first axis a₁into a voltage and outputs a signal. That is, the first angle detection sensors 11A and 11B output signals corresponding to angles of the mirror portion 20 around the first axis a₁.

The second movable frame 24 is provided with a pair of second angle detection sensors 12A and 12B at positions facing each other across the second axis a₂in the vicinity of the second support portion 23. Each of the pair of second angle detection sensors 12A and 12B is composed of a piezoelectric element. Each of the second angle detection sensors 12A and 12B converts a force applied by deformation of the second support portion 23 accompanying the rotation of the mirror portion 20 around the second axis a₂into a voltage and outputs a signal. That is, the second angle detection sensors 12A and 12B output signals corresponding to angles of the mirror portion 20 around the second axis a₂.

In FIGS. 2 and 3, the wiring line and the electrode pad for giving the driving signal to the first actuator 31 and the second actuator 32 are not shown. In FIGS. 2 and 3, a wiring line and an electrode pad for outputting signals from the first angle detection sensors 11A and 11B and the second angle detection sensors 12A and 12B are not shown. A plurality of the electrode pads are provided on the fixed frame 26.

As shown in FIGS. 4 and 5, the MMD 4 is formed, for example, by performing an etching treatment on a silicon on insulator (SOI) substrate 40. The SOI substrate 40 is a substrate in which a silicon oxide layer 42 is provided on a first silicon active layer 41 made of single crystal silicon, and a second silicon active layer 43 made of single crystal silicon is provided on the silicon oxide layer 42.

The mirror portion 20, the first support portion 21, the first movable frame 22, the second support portion 23, the second movable frame 24, and the connecting portion 25 are formed of the second silicon active layer 43 remaining by removing the first silicon active layer 41 and the silicon oxide layer 42 from the SOI substrate 40 by an etching treatment. The second silicon active layer 43 functions as an elastic portion having elasticity. The fixed frame 26 is formed of three layers of the first silicon active layer 41, the silicon oxide layer 42, and the second silicon active layer 43.

The first actuator 31 and the second actuator 32 have the piezoelectric element 30 on the second silicon active layer 43. The piezoelectric element 30 has a laminated structure in which a lower electrode 51, a piezoelectric film 52, and an upper electrode 53 are sequentially laminated on the second silicon active layer 43. An insulating film is provided on the upper electrode 53, but is not shown.

The upper electrode 53 and the lower electrode 51 are formed of, for example, gold (Au) or platinum (Pt). The piezoelectric film 52 is formed of, for example, lead zirconate titanate (PZT), which is a piezoelectric material. The upper electrode 53 and the lower electrode 51 are electrically connected to the driving controller 5 described above via the wiring line and the electrode pad.

A driving voltage is applied to the upper electrode 53 from the driving controller 5. The lower electrode 51 is connected to the driving controller 5 via the wiring line and the electrode pad, and a reference potential (for example, a ground potential) is applied thereto.

In a case where a positive or negative voltage is applied to the piezoelectric film 52 in the polarization direction, deformation (for example, expansion and contraction) proportional to the applied voltage occurs. That is, the piezoelectric film 52 exerts a so-called inverse piezoelectric effect. The piezoelectric film 52 exerts an inverse piezoelectric effect by applying a driving voltage from the driving controller 5 to the upper electrode 53, and displaces the first actuator 31 and the second actuator 32.

As shown in FIG. 6, the first angle detection sensor 11A is also similarly composed of the piezoelectric element 30 consisting of the lower electrode 51, the piezoelectric film 52, and the upper electrode 53 laminated on the second silicon active layer 43. In a case where force (pressure) is applied to the piezoelectric film 52, polarization proportional to the pressure is generated. That is, the piezoelectric film 52 exerts a piezoelectric effect. The piezoelectric film 52 exerts a piezoelectric effect and generates a voltage in a case where force is applied by deformation of the first support portion 21 accompanying the rotation of the mirror portion 20 around the first axis a₁.

Since the first angle detection sensor 11B has the same configuration as the first angle detection sensor 11A, the first angle detection sensor 11B is not shown. In addition, since the second angle detection sensors 12A and 12B have the same configuration as the first angle detection sensor 11A, the second angle detection sensors 12A and 12B are not shown.

FIG. 7 shows an example in which one piezoelectric film 52 of the pair of first actuators 31 is extended and the other piezoelectric film 52 is contracted, thereby generating rotational torque around the first axis a₁in the first actuator 31. In this way, one of the pair of first actuators 31 and the other are displaced in opposite directions to each other, whereby the mirror portion 20 rotates around the first axis a₁.

In addition, FIG. 7 shows an example in which the first actuator 31 is driven in an anti-phase resonance mode in which the displacement direction of the pair of first actuators 31 and the rotation direction of the mirror portion 20 are opposite to each other. The first actuator 31 may be driven in an in-phase resonance mode in which the displacement direction of the pair of first actuators 31 and the rotation direction of the mirror portion 20 are the same direction.

A deflection angle (hereinafter, referred to as a first deflection angle) θ₁of the mirror portion 20 around the first axis a₁is controlled by the driving signal (hereinafter, referred to as a first driving signal) given to the first actuator 31 by the driving controller 5. The first driving signal is, for example, a sinusoidal AC voltage. The first driving signal includes a driving voltage waveform V_1A(t) applied to one of the pair of first actuators 31 and a driving voltage waveform V_1B(t) applied to the other. The driving voltage waveform V_1A(t) and the driving voltage waveform V_1B(t) are in an anti-phase with each other (that is, the phase difference is) 180°.

The first deflection angle θ₁is an angle at which the normal line of the reflecting surface 20A is inclined with respect to the Z direction in an XZ plane.

FIG. 8 shows an example in which one piezoelectric film 52 of the pair of second actuators 32 is extended and the other piezoelectric film 52 is contracted, thereby generating rotational torque around the second axis a₂in the second actuator 32. In this way, one of the pair of second actuators 32 and the other are displaced in opposite directions to each other, whereby the mirror portion 20 rotates around the second axis a₂.

In addition, FIG. 8 shows an example in which the second actuator 32 is driven in an anti-phase resonance mode in which the displacement direction of the pair of second actuators 32 and the rotation direction of the mirror portion 20 are opposite to each other. The second actuator 32 may be driven in an in-phase resonance mode in which the displacement direction of the pair of second actuators 32 and the rotation direction of the mirror portion 20 are the same direction.

A deflection angle (hereinafter, referred to as a second deflection angle) θ₂of the mirror portion 20 around the second axis a₂is controlled by the driving signal (hereinafter, referred to as a second driving signal) given to the second actuator 32 by the driving controller 5. The second driving signal is, for example, a sinusoidal AC voltage. The second driving signal includes a driving voltage waveform V_2A(t) applied to one of the pair of second actuators 32 and a driving voltage waveform V_2B(t) applied to the other. The driving voltage waveform V_2A(t) and the driving voltage waveform V_2B(t) are in an anti-phase with each other (that is, the phase difference is 180°).

The second deflection angle θ₂is an angle at which the normal line of the reflecting surface 20A is inclined with respect to the Z direction in a YZ plane.

FIGS. 9A and 9B show examples of the first driving signal and the second driving signal. FIG. 9A shows the driving voltage waveforms V_1A(t) and V_1B(t) included in the first driving signal. FIG. 9B shows the driving voltage waveforms V_2A(t) and V_2B(t) included in the second driving signal.

The driving voltage waveforms V_1A(t) and V_1B(t) are represented as follows, respectively.

V_1A=V_off1+V₁sin(2πf_d1t)

V_1B=V_off1+V₁sin(2πf_d1t+α)

Here, V₁is the amplitude voltage. V_off1is the bias voltage. f_d1is the driving frequency (hereinafter, referred to as the first driving frequency). t is time. α is the phase difference between the driving voltage waveforms V_1A(t) and V_1B(t). In the present embodiment, for example, α=180°.

By applying the driving voltage waveforms V_1A(t) and V_1B(t) to the pair of first actuators 31, the mirror portion 20 swings around the first axis a₁at the first driving frequency f_d1(see FIG. 7).

The driving voltage waveforms V_2A(t) and V_2B(t) are represented as follows, respectively.

V_2A=V_off2+V₂sin(2πf_d2t+φ)

V_2B=V_off2+V₂sin(2πf_d2tβ+φ)

Here, V₂is the amplitude voltage. V_off2is the bias voltage. f_d2is the driving frequency (hereinafter, referred to as the second driving frequency). t is time. β is the phase difference between the driving voltage waveforms V_2A(t) and V_2B(t). In the present embodiment, for example, β=180°. In addition, φ is the phase difference between the driving voltage waveforms V_1A(t) and V_1B(t) and the driving voltage waveforms V_2A(t) and V_2B(t). In the present embodiment, for example, V_off1=V_off2=0 V.

By applying the driving voltage waveforms V_2A(t) and V_2B(t) to the pair of second actuators 32, the mirror portion 20 swings around the second axis a₂at the second driving frequency f_d2(see FIG. 8).

The first driving frequency f_d1is set so as to match the resonance frequency around the first axis a₁of the mirror portion 20. The second driving frequency f_d2is set so as to match the resonance frequency around the second axis a₂of the mirror portion 20. In the present embodiment, f_d1>f_d2. That is, in the mirror portion 20, a swing frequency around the first axis a₁is higher than a swing frequency around the second axis a₂. The first driving frequency f_d1and the second driving frequency f_d2do not necessarily have to match the resonance frequency. For example, the first driving frequency f_d1and the second driving frequency f_d2may be frequencies within a frequency range in the vicinity of the resonance frequency (for example, a range of half-width of frequency distribution having the resonance frequency as a peak value). This frequency range is, for example, within a range of a so-called Q value.

FIG. 10 shows an example of a configuration of the driving controller 5. The driving controller 5 includes a mirror driving unit 4A and a light source driving unit 3A. The mirror driving unit 4A includes a first driving signal generation unit 60A, a first signal processing unit 61A, a first phase shift unit 62A, a first zero cross pulse output unit 63A, a second driving signal generation unit 60B, a second signal processing unit 61B, a second phase shift unit 62B, and a second zero cross pulse output unit 63B. The first driving signal generation unit 60A corresponds to the first signal generator of the present disclosure.

The first driving signal generation unit 60A, the first signal processing unit 61A, and the first phase shift unit 62A perform feedback control such that the swing of the mirror portion 20 around the first axis a₁maintains a resonance state. The second driving signal generation unit 60B, the second signal processing unit 61B, and the second phase shift unit 62B perform feedback control such that the swing of the mirror portion 20 around the second axis a₂maintains a resonance state. The second driving signal generation unit 60B corresponds to the second signal generator of the present disclosure.

The first driving signal generation unit 60A generates the first driving signal including the above-described driving voltage waveforms V_1A(t) and V_1B(t) based on a reference waveform, and applies the generated first driving signal to the pair of first actuators 31 via the first phase shift unit 62A. Thereby, the mirror portion 20 swings around the first axis a₁. The first angle detection sensors 11A and 11B output signals corresponding to angles of the mirror portion 20 around the first axis a₁.

The second driving signal generation unit 60B generates the second driving signal including the above-described driving voltage waveforms V_2A(t) and V_2B(t) based on a reference waveform, and applies the generated second driving signal to the pair of second actuators 32 via the second phase shift unit 62B. Thereby, the mirror portion 20 swings around the second axis a₂. The second angle detection sensors 12A and 12B output signals corresponding to angles of the mirror portion 20 around the second axis a₂.

The first driving signal generated by the first driving signal generation unit 60A and the second driving signal generated by the second driving signal generation unit 60B are phase-synchronized.

FIG. 11 shows an example of signals output from the pair of first angle detection sensors 11A and 11B. In FIG. 11, S1a₁and S1a₂represent signals output from the pair of first angle detection sensors 11A and 11B in a case where the mirror portion 20 swings only around the first axis a₁without swinging around the second axis a₂. The signals S1a₁and S1a₂are waveform signals similar to a sinusoidal wave having the first driving frequency f_d1and are in an anti-phase with each other.

In a case where the mirror portion 20 swings around the first axis a₁and the second axis a₂simultaneously, a vibration noise RN1 caused by the swing of the mirror portion 20 around the second axis a₂is superimposed on the output signals of the pair of first angle detection sensors 11A and 11B. S1b₁represents a signal in which the vibration noise RN1 is superimposed on the signal S1a₁. Slb₂represents a signal in which the vibration noise RN1 is superimposed on the signal S1a₂. For the purpose of the description of this embodiment, the vibration noise RN1 is emphasized.

As described above, in a case of the biaxial drive, the signals Slb₁and Slb₂on which the vibration noise RN1 is superimposed are output from the first angle detection sensors 11A and 11B, and amplitudes of the signals S1b₁and S1b₂fluctuate every cycle. Therefore, it is difficult to directly obtain the amplitude and the phase based on the signals S1b₁and S1b₂output from the first angle detection sensors 11A and 11B.

FIG. 12 shows an example of signals output from the pair of second angle detection sensors 12A and 12B. In FIG. 12, S2a₁and S2a₂represent signals output from the pair of second angle detection sensors 12A and 12B in a case where the mirror portion 20 swings only around the second axis a₂without swinging around the first axis a₁. The signals S2a₁and S2a₂are waveform signals similar to a sinusoidal wave having the second driving frequency f_d2and are in an anti-phase with each other.

In a case where the mirror portion 20 swings around the first axis a₁and the second axis a₂simultaneously, a vibration noise RN2 caused by the swing of the mirror portion 20 around the first axis a₁is superimposed on the output signals of the pair of second angle detection sensors 12A and 12B. S2b₁represents a signal in which the vibration noise RN2 is superimposed on the signal S2a₁. S2b₂represents a signal in which the vibration noise RN2 is superimposed on the signal S2a₂. For the purpose of the description of this embodiment, the vibration noise RN2 is emphasized.

As described above, in a case of the biaxial drive, the signals S12b₁and S2b₂on which the vibration noise RN2 is superimposed are output from the second angle detection sensors 12A and 12B, and amplitudes of the signals S2b₁and S2b₂fluctuate every cycle. Therefore, it is difficult to directly obtain the amplitude and the phase based on the signals S2b₁and S2b₂output from the second angle detection sensors 12A and 12B.

The first signal processing unit 61A generates a signal (hereinafter, a first angle detection signal) S1c from which the vibration noise RN1 has been removed based on S1a₁and S1a₂output from the pair of first angle detection sensors 11A and 11B. The second signal processing unit 61B generates a signal (hereinafter, a second angle detection signal) S2c from which the vibration noise RN2 has been removed based on S2a₁and S2a₂output from the pair of second angle detection sensors 12A and 12B.

FIG. 13 shows a configuration of the first signal processing unit 61A. The first signal processing unit 61A includes an analog arithmetic circuit. As shown in FIG. 13, the first signal processing unit 61A is composed of a buffer amplifier 71, a variable gain amplifier 72, a subtraction circuit 73, and a gain adjustment circuit 74. The gain adjustment circuit 74 is composed of a first band pass filter (BPF) circuit 75A, a second BPF circuit 75B, a first detection circuit 76A, a second detection circuit 76B, and a subtraction circuit 77. The subtraction circuit 73 and the subtraction circuit 77 are differential amplification circuits including an operational amplifier.

The signal S1b₁output from the first angle detection sensor 11A is input to a positive input terminal (non-inverting input terminal) of the subtraction circuit 73 via the buffer amplifier 71. In addition, the signal output from the buffer amplifier 71 is branched in the middle of the process before being input to the subtraction circuit 73, and is input to the first BPF circuit 75A in the gain adjustment circuit 74.

The signal S1b₂output from the first angle detection sensor 11B is input to a negative input terminal (inverting input terminal) of the subtraction circuit 73 via the variable gain amplifier 72. In addition, the signal output from the variable gain amplifier 72 is branched in the middle of the process before being input to the subtraction circuit 73, and is input to the second BPF circuit 75B in the gain adjustment circuit 74.

Each of the first BPF circuit 75A and the second BPF circuit 75B has a pass band B1 having the second driving frequency f_d2as a center frequency, as shown in FIG. 14. The pass band B1 is, for example, a frequency band of f_d2±5 kHz. Since the vibration noise RN1 has the second driving frequency f_d2, the vibration noise RN1 passes through the pass band B1. Therefore, the first BPF circuit 75A extracts and outputs the vibration noise RN1 (see FIG. 11) from the signal input from the buffer amplifier 71. The second BPF circuit 75B extracts and outputs the vibration noise RN1 (see FIG. 11) from the signal input from the variable gain amplifier 72.

Each of the first detection circuit 76A and the second detection circuit 76B is composed of, for example, a root mean squared value to direct current converter (RMS-DC converter). The first detection circuit 76A converts the amplitude of the vibration noise RN1 input from the first BPF circuit 75A into a DC voltage signal and inputs the signal to the positive input terminal of the subtraction circuit 77. The second detection circuit 76B converts the amplitude of the vibration noise RN1 input from the second BPF circuit 75B into a DC voltage signal and inputs the signal to the negative input terminal of the subtraction circuit 77.

The subtraction circuit 77 outputs a value d₁obtained by subtracting the DC voltage signal input from the second detection circuit 76B from the DC voltage signal input from the first detection circuit 76A. The value d₁corresponds to a difference between the amplitude of the vibration noise RN1 included in the signal S1b₁output from the first angle detection sensor 11A and the amplitude of the vibration noise RN1 included in the signal S1b₂output from the first angle detection sensor 11B. The subtraction circuit 77 inputs the value d₁as a gain adjustment value to a gain adjustment terminal of the variable gain amplifier 72.

The variable gain amplifier 72 adjusts an amplitude level of the signal S1b₂by multiplying the signal S1b₂input from the first angle detection sensor 11B by the value d₁input as the gain adjustment value. In this way, a feedback control is performed by the gain adjustment circuit 74, so that the amplitude of the vibration noise RN1 included in the signal S1b₂after passing through the variable gain amplifier 72 is adjusted so as to match the amplitude of the vibration noise RN1 included in the signal S1b₁after passing through the buffer amplifier 71.

The subtraction circuit 73 outputs a value obtained by subtracting the signal S1b₂input to the negative input terminal from the signal S1b₁input to the positive input terminal. Since the amplitudes of the vibration noise RN1 included in both signals match with each other by the feedback control, the vibration noise RN1 included in both signals is offset by the subtraction processing by the subtraction circuit 73. Therefore, the subtraction circuit 73 outputs the first angle detection signal S1c (see FIG. 15), which is a signal from which the vibration noise RN1 has been removed.

FIG. 15 shows a state in which the first angle detection signal S1c is generated based on S1b₁and S1b₂output from the pair of first angle detection sensors 11A and 11B. The first angle detection signal Sic corresponds to a signal obtained by doubling an amplitude of a signal obtained by removing the vibration noise RN1 from the signal S1b₁.

The first angle detection signal S1c generated by the first signal processing unit 61A is input to the first driving signal generation unit 60A and the first zero cross pulse output unit 63A. In a case where the swing of the mirror portion 20 around the first axis a₁maintains a resonance state, as shown in FIG. 15, the first angle detection signal S1c output from the first signal processing unit 61A has a phase delay of 90° with respect to the driving voltage waveform V_1A(t) included in the first driving signal.

As shown in FIG. 16, the second signal processing unit 61B is composed of a buffer amplifier 81, a variable gain amplifier 82, a subtraction circuit 83, and a gain adjustment circuit 84. The gain adjustment circuit 84 is composed of a first BPF circuit 85A, a second BPF circuit 85B, a first detection circuit 86A, a second detection circuit 86B, and a subtraction circuit 87. The subtraction circuit 83 and the subtraction circuit 87 are differential amplification circuits including an operational amplifier.

The signal S2b₁output from the second angle detection sensor 12A is input to a positive input terminal of the subtraction circuit 83 via the buffer amplifier 81. In addition, the signal output from the buffer amplifier 81 is branched in the middle of the process before being input to the subtraction circuit 83, and is input to the first BPF circuit 85A in the gain adjustment circuit 84.

The signal S2b₂output from the second angle detection sensor 12B is input to a negative input terminal of the subtraction circuit 83 via the variable gain amplifier 82. In addition, the signal output from the variable gain amplifier 82 is branched in the middle of the process before being input to the subtraction circuit 83, and is input to the second BPF circuit 85B in the gain adjustment circuit 84.

Each of the first BPF circuit 85A and the second BPF circuit 85B has a pass band B2 having the first driving frequency f_d1as a center frequency, as shown in FIG. 17. The pass band B2 is, for example, a frequency band of f_d1±5 kHz. Since the vibration noise RN2 has the first driving frequency f_d1, the vibration noise RN2 passes through the pass band B2. Therefore, the first BPF circuit 85A extracts and outputs the vibration noise RN2 (see FIG. 12) from the signal input from the buffer amplifier 81. The second BPF circuit 85B extracts and outputs the vibration noise RN2 (see FIG. 12) from the signal input from the variable gain amplifier 82.

Each of the first detection circuit 86A and the second detection circuit 86B is composed of, for example, an RMS-DC converter. The first detection circuit 86A converts the amplitude of the vibration noise RN2 input from the first BPF circuit 85A into a DC voltage signal and inputs the signal to the positive input terminal of the subtraction circuit 87. The second detection circuit 86B converts the amplitude of the vibration noise RN2 input from the second BPF circuit 85B into a DC voltage signal and inputs the signal to the negative input terminal of the subtraction circuit 87.

The subtraction circuit 87 outputs a value d₂obtained by subtracting the DC voltage signal input from the second detection circuit 86B from the DC voltage signal input from the first detection circuit 86A. The value d₂corresponds to a difference between the amplitude of the vibration noise RN2 included in the signal S2b₁output from the second angle detection sensor 12A and the amplitude of the vibration noise RN2 included in the signal S2b₂output from the second angle detection sensor 12B. The subtraction circuit 87 inputs the value d₂as a gain adjustment value to a gain adjustment terminal of the variable gain amplifier 82.

The variable gain amplifier 82 adjusts an amplitude level of the signal S2b₂by multiplying the signal S2b₂input from the second angle detection sensor 12B by the value d₂input as the gain adjustment value. In this way, a feedback control is performed by the gain adjustment circuit 84, so that the amplitude of the vibration noise RN2 included in the signal S2b₂after passing through the variable gain amplifier 82 is adjusted so as to match the amplitude of the vibration noise RN2 included in the signal S2b₁after passing through the buffer amplifier 81.

The subtraction circuit 83 outputs a value obtained by subtracting the signal S2b₂input to the negative input terminal from the signal S2b₁input to the positive input terminal. Since the amplitudes of the vibration noise RN2 included in both signals match with each other by the feedback control, the vibration noise RN2 included in both signals is offset by the subtraction processing by the subtraction circuit 83. Therefore, the subtraction circuit 83 outputs the second angle detection signal S2c (see FIG. 18), which is a signal from which the vibration noise RN2 has been removed.

FIG. 18 shows a state in which the second angle detection signal S2c is generated based on S2b₁and S2b₂output from the pair of second angle detection sensors 12A and 12B. The second angle detection signal S2c corresponds to a signal obtained by doubling an amplitude of a signal obtained by removing the vibration noise RN2 from the signal S2b₁.

The second angle detection signal S2c generated by the second signal processing unit 61B is input to the second driving signal generation unit 60B and the second zero cross pulse output unit 63B. In a case where the swing of the mirror portion 20 around the second axis a₂maintains a resonance state, as shown in FIG. 18, the second angle detection signal S2c output from the second signal processing unit 61B has a phase delay of 90° with respect to the driving voltage waveform V_2A(t) included in the second driving signal.

Returning to FIG. 10, the first angle detection signal Sic input from the first signal processing unit 61A is fed back to the first driving signal generation unit 60A. The first phase shift unit 62A shifts the phase of the driving voltage waveform output from the first driving signal generation unit 60A. The first phase shift unit 62A shifts the phase by 90°, for example.

FIG. 19 shows an example of a configuration of the first driving signal generation unit 60A. As shown in FIG. 19, the first driving signal generation unit 60A includes a signal generation circuit 91A and a phase synchronization circuit 92A. The first driving signal generation unit 60A is a so-called phase locked loop (PLL) type drive circuit.

A sampling reset signal having the first driving frequency f_d1is input to the phase synchronization circuit 92A from the signal generation circuit 91A, and the first angle detection signal S1c is input from the first signal processing unit 61A (see FIG. 10). The phase synchronization circuit 92A adjusts a phase of a sampling clock signal generated by itself based on the sampling reset signal and the first angle detection signal S1c.

The signal generation circuit 91A generates the driving voltage waveforms V_1A(t) and V_1B(t) constituting the first driving signal based on the sampling clock signal input from the phase synchronization circuit 92A.

In this way, the feedback control is performed such that a phase difference between the first driving signal and the first angle detection signal Sic is maintained at 900 by the first phase shift unit 62A and the first driving signal generation unit 60A of the PLL type. By maintaining the phase difference between the first driving signal and the first angle detection signal S1c at 90°, the swing of the mirror portion 20 around the first axis a₁is maintained in a resonance state.

The second angle detection signal S2c input from the second signal processing unit 61B is fed back to the second driving signal generation unit 60B. The second phase shift unit 62B shifts the phase of the driving voltage waveform output from the second driving signal generation unit 60B. The second phase shift unit 62B shifts the phase by 90°, for example.

FIG. 20 shows an example of a configuration of the second driving signal generation unit 60B. As shown in FIG. 20, the second driving signal generation unit 60B includes a signal generation circuit 91B and a phase synchronization circuit 92B. The second driving signal generation unit 60B is a so-called PLL type drive circuit.

A sampling reset signal having the second driving frequency f_d2is input to the phase synchronization circuit 92B from the signal generation circuit 91B, and the second angle detection signal S2c is input from the second signal processing unit 61B (see FIG. 10). The phase synchronization circuit 92B adjusts a phase of a sampling clock signal generated by itself based on the sampling reset signal and the second angle detection signal S2c.

The signal generation circuit 91B generates the driving voltage waveforms V_2A(t) and V_2B(t) constituting the second driving signal based on the sampling clock signal input from the phase synchronization circuit 92B.

In this way, the feedback control is performed such that a phase difference between the second driving signal and the second angle detection signal S2c is maintained at 900 by the second phase shift unit 62B and the second driving signal generation unit 60B of the PLL type. By maintaining the phase difference between the second driving signal and the second angle detection signal S2c at 90°, the swing of the mirror portion 20 around the second axis a₂is maintained in a resonance state.

Returning to FIG. 10, the first zero cross pulse output unit 63A generates a zero cross pulse (hereinafter, referred to as a first zero cross pulse) ZC1 based on the first angle detection signal S1c input from the first signal processing unit 61A. The first zero cross pulse output unit 63A is composed of a zero cross detection circuit.

As shown in FIG. 21, the first zero cross pulse output unit 63A generates the first zero cross pulse ZC1 at a timing at which the first angle detection signal S1c, which is an AC signal, crosses zero volt. The first zero cross pulse output unit 63A inputs the generated first zero cross pulse ZC1 to the light source driving unit 3A.

The second zero cross pulse output unit 63B generates a zero cross pulse (hereinafter, referred to as a second zero cross pulse) ZC2 based on the second angle detection signal S2c input from the second signal processing unit 61B. The second zero cross pulse output unit 63B is composed of a zero cross detection circuit.

As shown in FIG. 22, the second zero cross pulse output unit 63B generates the second zero cross pulse ZC2 at a timing at which the second angle detection signal S2c, which is an AC signal, crosses zero volt. The second zero cross pulse output unit 63B inputs the generated second zero cross pulse ZC2 to the light source driving unit 3A.

The light source driving unit 3A drives the light source 3 based on drawing data supplied from the outside of the image drawing system 10, for example. In addition, the light source driving unit 3A controls the irradiation timing such that the irradiation timing of the laser light is synchronized with the first zero cross pulse ZC1 and the second zero cross pulse ZC2 input from the mirror driving unit 4A.

As described above, according to the technique of the present disclosure, by subtracting one of the pair of first output signals output from the pair of first angle detection sensors from the other, the vibration noise caused by the swing of the mirror portion around the second axis is removed. As a result, since the first angle detection signal representing the angle of the mirror portion around the first axis, from which the vibration noise is removed, is generated, the swing of the mirror portion can be accurately controlled. In addition, by maintaining the swing of the mirror portion in a resonance state, the amplitude (maximum deflection angle) of the swing of the mirror portion is maintained constant.

Second Embodiment

Next, an image drawing system according to a second embodiment will be described. In the image drawing system of the present embodiment, the disposition of the pair of first angle detection sensors 11A and 11B and the pair of second angle detection sensors 12A and 12B in the MMD 4 is different from that of the first embodiment. In the first embodiment, the pair of first angle detection sensors 11A and 11B are disposed at positions facing each other across the first axis a₁, whereas, in the second embodiment, the pair of first angle detection sensors 11A and 11B are disposed at positions facing each other across the second axis a₂. In the first embodiment, the pair of second angle detection sensors 12A and 12B are disposed at positions facing each other across the second axis a₂, whereas, in the second embodiment, the pair of second angle detection sensors 12A and 12B are disposed at positions facing each other across the first axis a₁.

FIG. 23 is a plan view showing the configuration of the MMD 4 according to the present embodiment. As shown in FIG. 23, the pair of first angle detection sensors 11A and 11B are disposed in the vicinity of the first support portion 21 on the first movable frame 22. The first angle detection sensor 11A is disposed in the vicinity of the first support portion 21 connected to one side of the mirror portion 20. The first angle detection sensor 11B is disposed in the vicinity of the first support portion 21 connected to the other side of the mirror portion 20. Therefore, the pair of first angle detection sensors 11A and 11B are disposed at positions facing each other across the second axis a₂and facing each other across the mirror portion 20. In addition, the pair of first angle detection sensors 11A and 11B are disposed at positions deviated from the first axis a₁in the same direction (in the present embodiment, −X direction).

The pair of second angle detection sensors 12A and 12B are disposed in the vicinity of the second support portion 23 on the second movable frame 24. The second angle detection sensor 12A is disposed in the vicinity of the second support portion 23 connected to one side of the first movable frame 22. The second angle detection sensor 12B is disposed in the vicinity of the second support portion 23 connected to the other side of the first movable frame 22. Therefore, the pair of second angle detection sensors 12A and 12B are disposed at positions facing each other across the first axis a₁and facing each other across the mirror portion 20 and the first movable frame 22. In addition, the pair of second angle detection sensors 12A and 12B are disposed at positions deviated from the second axis a₂in the same direction (in the present embodiment, +Y direction).

FIG. 24 shows an example of signals output from the pair of first angle detection sensors 11A and 11B in the present embodiment. In FIG. 24, S1a represents a signal output from the pair of first angle detection sensors 11A and 11B in a case where the mirror portion 20 swings only around the first axis a₁without swinging around the second axis a₂. In the present embodiment, since the first angle detection sensors 11A and 11B are disposed at positions deviated in the same direction with respect to the first axis a₁, waveform signals having the same phase and having the first driving frequency f_d1are output from the first angle detection sensors 11A and 11B.

In a case where the mirror portion 20 swings around the first axis a₁and the second axis a₂simultaneously, a vibration noise RN1a caused by the swing of the mirror portion 20 around the second axis a₂is superimposed on the output signal of the first angle detection sensor 11A. Similarly, in a case where the mirror portion 20 swings around the first axis a₁and the second axis a₂simultaneously, a vibration noise RN1b caused by the swing of the mirror portion 20 around the second axis a₂is superimposed on the output signal of the first angle detection sensor 11B. Since the first angle detection sensors 11A and 11B are disposed at positions facing each other across the second axis a₂, the vibration noises RN1a and RN1b superimposed on the first angle detection sensors 11A and 11B are in an anti-phase with each other.

As described above, in a case of the biaxial drive, the signal S1b₁on which the vibration noise RN1a is superimposed is output from the first angle detection sensor 11A, and the signal S1b₂on which the vibration noise RN1b is superimposed is output from the first angle detection sensor 11B.

FIG. 25 shows an example of signals output from the pair of second angle detection sensors 12A and 12B in the present embodiment. In FIG. 25, S2a represents a signal output from the pair of second angle detection sensors 12A and 12B in a case where the mirror portion 20 swings only around the second axis a₂without swinging around the first axis a₁. In the present embodiment, since the second angle detection sensors 12A and 12B are disposed at positions deviated in the same direction with respect to the second axis a₂, waveform signals having the same phase and having the second driving frequency f_d2are output from the second angle detection sensors 12A and 12B.

In a case where the mirror portion 20 swings around the first axis a₁and the second axis a₂simultaneously, a vibration noise RN2a caused by the swing of the mirror portion 20 around the first axis a₁is superimposed on the output signal of the second angle detection sensor 12A. Similarly, in a case where the mirror portion 20 swings around the first axis a₁and the second axis a₂simultaneously, a vibration noise RN2b caused by the swing of the mirror portion 20 around the first axis a₁is superimposed on the output signal of the second angle detection sensor 12B. Since the second angle detection sensors 12A and 12B are disposed at positions facing each other across the first axis a₁, the vibration noises RN2a and RN2b superimposed on the second angle detection sensors 12A and 12B are in an anti-phase with each other.

As described above, in a case of the biaxial drive, the signal S2b₁on which the vibration noise RN2a is superimposed is output from the second angle detection sensor 12A, and the signal S2b₂on which the vibration noise RN2b is superimposed is output from the second angle detection sensor 12B.

In the present embodiment, the driving controller 5 is different from the configuration of the driving controller 5 of the first embodiment only in the configuration of the first signal processing unit 61A and the second signal processing unit 61B. As shown in FIG. 26, in the present embodiment, the first signal processing unit 61A includes an addition circuit 73A instead of the subtraction circuit 73. The addition circuit 73A outputs a value obtained by adding the signal S1b₁input from the first angle detection sensor 11A via the buffer amplifier 71 and the signal S1b₂input from the first angle detection sensor 11B via the variable gain amplifier 72.

In the present embodiment, the gain adjustment circuit 74 adjusts an amplitude level of the vibration noise RN1b included in the signal S1b₂so as to match an amplitude level of the vibration noise RN1a included in the signal S1b₁. Therefore, the vibration noises RN1a and RN1b are offset by addition processing by the addition circuit 73A. Therefore, the addition circuit 73A outputs the first angle detection signal S1c which is a signal from which the vibration noises RN1a and RNib have been removed.

FIG. 27 shows a state in which the first angle detection signal S1c is generated based on S1b₁and S1b₂output from the pair of first angle detection sensors 11A and 11B in the present embodiment. Also in the present embodiment, the same first angle detection signal S1c as in the first embodiment is obtained (see FIG. 15).

As shown in FIG. 28, in the present embodiment, the second signal processing unit 61B includes an addition circuit 83A instead of the subtraction circuit 83. The addition circuit 83A outputs a value obtained by adding the signal S2b₁input from the second angle detection sensor 12A via the buffer amplifier 81 and the signal S2b₂input from the second angle detection sensor 12B via the variable gain amplifier 82.

In the present embodiment, the gain adjustment circuit 84 adjusts an amplitude level of the vibration noise RN2b included in the signal S2b₂so as to match an amplitude level of the vibration noise RN2a included in the signal S2b₁. Therefore, the vibration noises RN2a and RN2b are offset by addition processing by the addition circuit 83A. Therefore, the addition circuit 83A outputs the second angle detection signal S2c which is a signal from which the vibration noises RN2a and RN2b have been removed.

FIG. 29 shows a state in which the second angle detection signal S2c is generated based on S2b₁and S2b₂output from the pair of second angle detection sensors 12A and 12B in the present embodiment. Also in the present embodiment, the same second angle detection signal S2c as in the first embodiment is obtained (see FIG. 15).

As described above, the pair of first angle detection sensors 11A and 11B need only be disposed at positions facing each other across the first axis a₁or the second axis a₂. In a case where the pair of first angle detection sensors 11A and 11B are disposed at positions facing each other across the first axis a₁, the vibration noise can be removed by subtracting one of the output signals of the first angle detection sensors 11A and 11B from the other. In a case where the pair of first angle detection sensors 11A and 11B are disposed at positions facing each other across the second axis a₂, the vibration noise can be removed by adding the output signals of the first angle detection sensors 11A and 11B.

Similarly, the pair of second angle detection sensors 12A and 12B need only be disposed at positions facing each other across the first axis a₁or the second axis a₂. In a case where the pair of second angle detection sensors 12A and 12B are disposed at positions facing each other across the second axis a₂, the vibration noise can be removed by subtracting one of the output signals of the second angle detection sensors 12A and 12B from the other. In a case where the pair of second angle detection sensors 12A and 12B are disposed at positions facing each other across the first axis a₁, the vibration noise can be removed by adding the output signals of the second angle detection sensors 12A and 12B.

Modification Example

Next, a modification example of each of the above-described embodiments will be described. In each of the above-described embodiments, the gain adjustment circuit 74 extracts a vibration noise having the second driving frequency f_d2by the first BPF circuit 75A and the second BPF circuit 75B. Alternatively, the vibration noise having the second driving frequency f_d2may be extracted by a low-pass filter circuit having a cutoff frequency between the first driving frequency f_d1and the second driving frequency f_d2. In addition, in each of the above-described embodiments, the gain adjustment circuit 84 extracts a vibration noise having the first driving frequency f_d1by the first BPF circuit 85A and the second BPF circuit 85B. Alternatively, the vibration noise having the first driving frequency f_d1may be extracted by a high-pass filter circuit having a cutoff frequency between the first driving frequency f_d1and the second driving frequency f_d2.

The configuration of the MMD 4 shown in the above embodiment is an example. The configuration of the MMD 4 can be modified in various ways. For example, the first actuator 31 that allows the mirror portion 20 to swing around the first axis a₁may be disposed on the second movable frame 24, and the second actuator 32 that allows the mirror portion 20 to swing around the second axis a₂may be disposed on the first movable frame 22.

The hardware configuration of the driving controller 5 can be variously modified. In each of the above-described embodiments, the driving controller 5 includes an analog arithmetic circuit, and can also include a digital arithmetic circuit. The driving controller 5 may be composed of one processor or may be composed of a combination of two or more processors of the same type or different types. The processor includes, for example, a central processing unit (CPU), a programmable logic device (PLD), or a dedicated electric circuit. As is well known, the CPU is a general-purpose processor that executes software (program) to function as various processing units. The PLD is a processor such as a field programmable gate array (FPGA) whose circuit configuration can be changed after manufacture. The dedicated electric circuit is a processor that has a dedicated circuit configuration designed to perform a specific process, such as an application specific integrated circuit (ASIC).

Comparative Example

Next, a comparative example with the technology of the present disclosure will be described. In the technique of the present disclosure, a vibration noise is removed by adding or subtracting a pair of output signals output from a pair of angle detection sensors as described above. With respect to this, it is considered to remove a vibration noise by performing frequency filter processing on the output signal output from the angle detection sensor. Hereinafter, as a comparative example, an example of removing a vibration noise by frequency filter processing will be described.

In the present comparative example, at least any one of the pair of first angle detection sensors 11A and 11B need only be provided. In addition, at least any one of the pair of second angle detection sensors 12A and 12B need only be provided.

In the present comparative example, the first signal processing unit 61A is a band pass filter circuit that has a pass band having the first driving frequency f_d1as a center frequency. Similarly, the second signal processing unit 61B is a band pass filter circuit that has a pass band having the second driving frequency f_d2as a center frequency. As a result, a signal from which the vibration noise having the second driving frequency f_d2has been removed is output from the first signal processing unit 61A. A signal from which the vibration noise having the first driving frequency f_d1has been removed is output from the second signal processing unit 61B.

In this way, a vibration noise can be removed by using the first signal processing unit 61A and the second signal processing unit 61B as a band pass filter circuit, but accurate phase information may not be obtained from a signal from which the vibration noise has been removed. This is due to a phase response of the band pass filter circuit.

FIG. 30 shows an example of gain and phase characteristics of the band pass filter circuit. A center frequency of the band pass filter circuit shown in FIG. 30 is 10 kHz. A phase changes abruptly in the vicinity of the center frequency. Therefore, in a case where a frequency of a signal input to the band pass filter circuit deviates from the center frequency, a phase of an output signal from the band pass filter circuit changes significantly. In this way, since the phase of the output signal from the angle detection sensor may change significantly due to passing through the band pass filter circuit, it is difficult to use the output signal from the band pass filter circuit as timing information for maintaining a resonance state.

In a case where a zero cross pulse is generated based on the output signal from the band pass filter circuit and input to the light source driving unit 3A, an image out of synchronization with the scanning of light by the MMD 4 is drawn on the surface to be scanned 6. In this case, it is necessary to provide a phase shifter capable of manually adjusting the phase of the output signal from the band pass filter circuit and to manually adjust the phase shifter so that there is no deviation while a user observes the image drawn on the surface to be scanned 6.

On the other hand, in the technique of the present disclosure, a vibration noise is removed by adding or subtracting a pair of output signals output from a pair of angle detection sensors without using a band pass filter circuit. Therefore, the phase of the output signal does not change significantly by the removal of the vibration noise, and the output signal can be used as timing information for maintaining a resonance state. Therefore, it is not necessary for the user to manually adjust the phase shifter.

All documents, patent applications, and technical standards mentioned in this specification are incorporated herein by reference to the same extent as in a case where each document, each patent application, and each technical standard are specifically and individually described by being incorporated by reference.