RELATED APPLICATION

This application is a Continuation Application of the co-pending commonly-owned U.S. patent application with Ser. No. 12/435,537, filed on May 5, 2009, which claims priority to U.S. Provisional Application No. 61/126,446, filed on May 5, 2008, both of which are fully incorporated by reference.

BACKGROUND

Some conventional chargers, e.g., switch mode battery chargers, control a charging current by monitoring a current through a current sensor. The charger can include an input current amplifier that is coupled to the current sensor and for monitoring the charging current. Such sensing method may be accurate when the voltage drop on the sense element is relatively big, e.g., greater than 50 mV. However, problems may occur when the charger controls a relatively small charging current, e.g., during wake-up charging, trickle charging, or end of charging.

One of the issues is caused by an offset of the input current amplifier, which can be in the range of 2 mV-3 mV. For example, when the charging current is relatively small, the sensing error may reach up to 100%.

SUMMARY

In one embodiment, a high-side switch is coupled to a power supply terminal and selectively coupled to ground via a conduction path. During an on state duration, the high-side switch is enabled and the conduction path is disabled. During an off state duration, the high-side switch is disabled and the conduction path is enabled. During a skip state duration, the high-side switch and the conduction path both are disabled. A controller coupled to the high-side switch is configured to control the on state duration and the skip state duration based on a current reference. The controller is further configured to generate a control signal for controlling the high-side switch and the conduction path according to the on state duration and the skip state duration, and adjust an output current to the current reference according to the control signal.

BRIEF DESCRIPTION OF THE DRAWINGS

Features and advantages of embodiments of the claimed subject matter will become apparent as the following detailed description proceeds, and upon reference to the drawings, wherein like numerals depict like parts, and in which:

FIG. 1 illustrates a block diagram example of a power converter, in accordance with one embodiment of the present invention.

FIG. 2 illustrates plot examples of an inductor voltage, an inductor current and an equivalent level of the inductor current, in accordance with one embodiment of the present invention.

FIG. 3 illustrates a block diagram example of a power converter, in accordance with one embodiment of the present invention.

FIG. 4 illustrates a block diagram example of part of a controller in a power converter, in accordance with one embodiment of the present invention.

FIG. 5 illustrates plot examples of a first control signal, a second control signal and an inductor current, in accordance with one embodiment of the present invention.

FIG. 6 illustrates a flowchart example of operations performed by a power converter, in accordance with one embodiment of the present invention.

DETAILED DESCRIPTION

Reference will now be made in detail to the embodiments of the present invention. While the invention will be described in conjunction with these embodiments, it will be understood that they are not intended to limit the invention to these embodiments. On the contrary, the invention is intended to cover alternatives, modifications and equivalents, which may be included within the spirit and scope of the invention as defined by the appended claims.

Furthermore, in the following detailed description of the present invention, numerous specific details are set forth in order to provide a thorough understanding of the present invention. However, it will be recognized by one of ordinary skill in the art that the present invention may be practiced without these specific details. In other instances, well known methods, procedures, components, and circuits have not been described in detail as not to unnecessarily obscure aspects of the present invention.

In one embodiment, the present invention provides a power converter that converts input power to output power at a different level. An output voltage/current of the power converter can be used to charge a battery or power a load. The power converter includes a high-side switch and a conduction path (or a low-side switch) coupled to the high-side switch. The high-side switch is coupled to a power source providing the input power and is selectively coupled to ground via the conduction path. During an on state duration, the high-side switch is enabled (turned on) and the conduction path is disabled (cut off). During an off state duration, the high-side switch is disabled (turned off) and the conduction path is enabled. During a skip state duration, the high-side switch and the conduction path both are disabled (cut off).

Advantageously, the output current of the power converter can be controlled in different ways depending on the level of the output current. When the output current is relatively large, e.g., greater than a threshold, or when the output current is to be adjusted to a relatively large current reference, the power converter can adjust the output current by sensing the output current using an amplifier and by comparing the sensed output current with the current reference. When the output current is relatively small, e.g., less than a threshold, or when the output current is to be adjusted to a relatively small current reference, the power converter can adjust the output current by controlling the on state duration and the skip state duration according to the current reference. For example, a controller can calculate or adjust the on state duration and the skip state duration according to the current reference and generate corresponding control signals to control the high-side switch and the conduction path. Consequently, the output current can be adjusted to the current reference in a relatively accurate way.

FIG. 1 illustrates a block diagram example of a power converter 100, in accordance with one embodiment of the present invention. In one embodiment, the power converter 100 is a DC to DC converter. However, the invention is not so limited. The invention can also be well suited in other types of converters. As shown in FIG. 1, the DC to DC converter 100 can receive an input voltage V_INat terminal 110 and generate an output voltage V_OUTat terminal 112. The DC to DC converter 100 can include a controller 102, a driver 104, a pair of switches 106 (including a high-side switch Q₁and a low-side switch Q₂) and a low pass filter 108. The low pass filter 108 can include an inductor L and a capacitor C. The output voltage V_OUTat terminal 112 can be used to power a load or charge a battery.

In one embodiment, the high-side switch Q₁is coupled to a power supply terminal 110 and selectively coupled to ground via the low-side switch Q₂. During an on state duration T_ON, the high-side switch Q₁can be enabled (turned on) and the low-side switch Q₂can be disabled (turned off). During an off state duration T_OFF, the high-side switch Q₁can be disabled (turned off) and the low-side switch Q₂can be enabled (turned on). During a skip state duration T_SKIP, the high-side switch Q₁and the low-side switch Q₂both can be disabled (turned off). The controller 102 that is coupled to the high-side switch Q₁via the driver 104 can control the durations T_ON, T_OFFand T_SKIPbased on a current reference I_REF. The controller 102 can also generate a first control signal, e.g., a pulse width modulation (PWM) signal from a terminal PWM of the controller 102, to control the high-side switch Q₁and the low-side switch Q₂according to the durations T_ON, T_OFFand T_SKIP. Additionally, the controller 102 can generate a second control signal, e.g., a low-side switch enable (LDR_EN) signal from a terminal LDR_EN of the controller 102, to control the low-side switch Q₂according to the durations T_ON, T_OFFand T_SKIP. As such, the controller 102 can adjust an output current I_OUTof the power converter 100 to the current reference I_REFaccording to the PWM signal and the LDR_EN signal.

Specifically, if the LDR_EN signal is logic high, the state of the PWM signal can control the switches Q₁and Q₂. For instance, the switch Q₁can be turned on and the switch Q₂can be turned off if the PWM signal is logic high. The switch Q₁can be turned off and the switch Q₂can be turned on if the PWM signal is logic low. In addition, if the LDR_EN signal is logic low and the PWM signal is logic high, the switch Q₁can be turned on and the switch Q₂can be turned off. However, if the PWM signal is logic low in this instance, the switches Q₁and Q₂both can be turned off.

In other words, in one embodiment, during the on state duration T_ON, the PWM signal is logic high and the LDR_EN signal can be logic high or logic low. During the off state duration T_OFF, the PWM signal is logic low and the LDR_EN signal is logic high. During the skip state duration T_SKIP, the PWM signal and the LDR_EN signal both are logic low.

In one embodiment, the inductor L is coupled to the high-side switch Q₁and the low-side switch Q₂, such that the switch end of the inductor L can be alternately coupled to the power supply terminal 110 and ground depending on the state of the switches Q₂and Q₁.

More specifically, during the on state duration T_ON, the inductor L can be coupled to the power supply terminal 110. Neglecting the voltage drop on the sense resistor R₁which has relatively low resistance, the voltage difference between the terminals of the inductor L can be approximately equal to the input voltage V_INat the power supply terminal 110 less the output voltage V_OUTat the output terminal 112. In one embodiment, the input voltage V_INis greater than the output voltage V_OUT, so there is a net positive voltage across the inductor L. As such, the inductor current I_Lcan ramp up (increase) according to equation (1) as shown below:

di/dt=(V_INâˆ’V_OUT)/L=Î”I₁/T_ON,â€ƒâ€ƒ(1)

where Î”I₁is the change of the inductor current I_Lduring the on state duration T_ON.

In addition, during the off state duration T_OFF, the inductor L can be coupled to ground and there can be a net negative voltage âˆ’V_OUTacross the inductor L. As such, the inductor current I_Lcan ramp down (decrease) according to equation (2) as shown below:

di/dt=V_OUT/L=Î”I₂/T_OFF,â€ƒâ€ƒ(2)

where Î”I₂is the change of the inductor current I_Lduring the off state duration T_OFF. Furthermore, during the skip state duration T_SKIP, since both of the switches Q₁and Q₂are turned off, the switching side of the inductor L can be left floating. As such, the inductor current I_Lcan be approximately zero. As used herein, â€œapproximately zeroâ€ means that the current I_Lmay be different from zero so long as a leakage current that may flow through the inductor L when switches Q₁and Q₂are off is relatively small and can be omitted.

In one embodiment, the controller 102 can adjust a limit, e.g., a peak current level I_PK, of the inductor current I_Laccording to the on state duration T_ON, the input voltage V_INand the output voltage V_OUT. For example, according to equation (1), the current change Î”I₁during the on state duration T_ONcan be given by:

Î”I₁=T_ON*(V_INâˆ’V_OUT)/L.â€ƒâ€ƒ(3)

Assume that the level of the current change Î”I_iis the peak current level I_PK, the peak current level I_PKcan be given by:

I_PK=T_ON*(V_INâˆ’V_OUT)/L.â€ƒâ€ƒ(4)

In one such embodiment, during the on state duration T_ON, the inductor current I_Lcan increase from zero to the peak current level I_PK. If the input voltage V_INand the output voltage V_OUTare determined, the peak current level I_PKcan increase as the on state duration T_ONincreases, and can decrease as the on state duration T_ONdecreases.

Similarly, according to equation (2), the current change Î”I₂during the off state duration T_OFFcan be given by:

Î”I₂=T_OFF*V_OUT/L.â€ƒâ€ƒ(5)

Advantageously, the controller 102 can control the off state duration T_OFFaccording to the on state duration T_ON, the input voltage V_INand the output voltage V_OUT, such that the inductor current I_Lcan decrease from the peak current level I_PKto zero during the off state duration T_OFF. In one such embodiment, according to equation (5), the peak current level I_PKcan also be given by:

I_PK=T_OFF*V_OUT/L.â€ƒâ€ƒ(6)

Based on equations (4) and (6), the following equation can be obtained:

T_OFF=T_ON*(V_INâˆ’V_OUT)/V_OUT.â€ƒâ€ƒ(7)

In other words, the controller 102 can control the off state duration T_OFFproportional to the on state duration T_ONbased on equation (7).

FIG. 2 illustrates plot examples of the inductor voltage V_Lacross the inductor L, the inductor current I_Land an equivalent level I_L_â€”_EQVof the inductor current I_L, in accordance with one embodiment of the present invention. FIG. 2 is described in combination with FIG. 1.

Plots 202, 204 and 206 respectively show the waveforms of the inductor voltage V_L, the inductor current I_Land the equivalent level I_L_â€”_EQVof the inductor current I_L, in one embodiment. Specifically, during the on state duration T_ON, the inductor voltage V_Lcan be equal to V_INâˆ’V_OUT, and the inductor current I_Lcan increase. During the off state duration T_OFF, the inductor voltage V_Lcan be equal to âˆ’V_OUT, and the inductor current I_Lcan decrease. The inductor current I_Lcan have a current limit, e.g., the peak current level I_PK, determined by the on state duration T_ON, the input voltage V_INand the output voltage V_OUT. During the skip state duration T_SKIP, the inductor current I_Land inductor voltage V_Lcan be approximately zero.

According to the waveform 204 for the inductor current I_L, the equivalent level I_L_â€”_EQVof the inductor current I_Lcan be given by:

I_L_â€”_EQV=(I_PK/2)*(T_ON+T_OFF)/(T_ON+T_OFF+T_SKIP).â€ƒâ€ƒ(8)

When equations (4) and (7) are substituted into equation (8), the following equation can be obtained:

$\begin{matrix} \begin{matrix} I_{L_EQV} = î¢ž [(V_{IN} - V_{OUT}) / (2 * L)] * T_{ON} / \\ î¢ž [1 + (V_{OUT} / V_{IN}) * (T_{SKIP} / T_{ON})] \\ = î¢ž K_{1} * T_{ON} / [1 + K_{2} * (T_{SKIP} / T_{ON})], \end{matrix} & (9) \end{matrix}$

where K₁is a parameter that is equal to (V_INâˆ’V_OUT)/(2*L), and K₂is a parameter that is equal to V_OUT/V_IN. As such, the equivalent current I_L_â€”_EQVcan be controlled by adjusting the on state duration T_ONand/or the skip state duration T_SKIP. In one embodiment, the output current I_OUTis equal to I_L_â€”_EQV.

Referring back to FIG. 1, if the skip state duration T_SKIPis determined or fixed, the controller 102 can increase the equivalent current I_L_â€”_EQVby increasing the on state duration T_ON, and also can decrease the equivalent current I_L_â€”_EQVby decreasing the on state duration T_ON. If the on state duration T_ONis determined or fixed, the equivalent current I_L_â€”_EQVcan decrease as the skip state duration T_SKIPincreases, and can increase as the skip state duration T_SKIPdecreases. In other words, based on equation (9), by setting the equivalent current I_L_â€”_EQVto the current reference I_REF, the controller 102 or a processor (not shown in FIG. 1) can calculate the on state duration T_ONand/or the skip state duration T_SKIP. As such, the controller 102 can control the PWM signal and the LDR_EN signal based on the calculated durations T_ONand T_SKIP, so as to adjust the equivalent current I_L_â€”_EQVto the current reference I_REF.

In one embodiment, the controller 102 can vary the peak current level I_PKby varying the on state duration T_ON. In another embodiment, the controller 102 can be a constant-ripple-current (CRC) controller that controls the power converter 100 to generate a current I_Lhaving a constant peak current level I_PK. Specifically, the controller 102 can control the on state duration T_ONinversely proportional to the input voltage V_INless the output voltage V_OUT. For example, the on state duration T_ONcan be given by:

T_ON=K/(V_INâˆ’V_OUT),â€ƒâ€ƒ(10a)

where K is a programmable constant parameter. The controller 102 can also control the off state duration T_OFFinversely proportional to the output voltage V_OUT. For example, the off state duration T_OFFcan be given by:

T_OFF=K/V_OUT.â€ƒâ€ƒ(10b)

As such, according to equation (4) or equation (6), the following equation can be obtained:

I_PK=K/L.â€ƒâ€ƒ(11)

As a result, the inductor current I_Lcan have a constant peak current level I_PK.

When equations (10a), (10b) and (11) are substituted into equation (8), the following equation can be obtained:

I_L_â€”_EQV=K²*V_IN/[2*L*(K*V_IN+T_SKIP*V_OUT*(V_INâˆ’V_OUT))].â€ƒâ€ƒ(12)

In one such embodiment, if the input voltage V_INand the output voltage V_OUTare determined, e.g., the input voltage V_INis obtained via the VIN terminal of the controller 102 and the output voltage V_OUTis obtained via the VFB terminal of the controller 102, the controller 102 can adjust the equivalent current I_L_â€”_EQVby controlling the skip state duration T_SKIP.

Moreover, the controller 102 can have a target input terminal SLEW where the desired output voltage V_OUTis set. In one embodiment, the slew capacitor C_SLEWcoupled to the terminal SLEW charges based on the value of the resistors in the resistor divider R₂/R₃and the value of the reference voltage at a VREF terminal of the controller 102. Various ways can be used to charge the slew capacitor C_SLEWand create a target voltage signal V_TARGETat the terminal SLEW. In addition, the terminal VFB of the controller 102 can receive a feedback signal representative of the output voltage level V_OUT. The controller 102 can include a comparator for comparing the output voltage level V_OUTwith the target voltage level V_TARGET, so as to adjust the output voltage level V_OUTto the target voltage level V_TARGET. Furthermore, an optional sense resistor R₁or an inductor DCR (direct current resistance) current sensing circuit (not shown in FIG. 1) can be utilized to provide feedback voltage levels to terminals CSN and CSP of the controller 102, so as to represent the inductor current level I_L. For example, the difference between the voltage levels at the terminals CSN and CSP is proportional to the inductor current level I_L.

In one embodiment, the output terminal 112 is coupled to a load to power the load. In another embodiment, the output terminal 112 is coupled to a battery to charge the battery. In one such embodiment, the output current I_OUT, e.g., I_L_â€”_EQV, can be used to charge the battery. In one embodiment, the power converter 100 can charge the battery in different charging modes, e.g., a normal current charging mode and a small current charging mode, etc.

In the normal current charging mode, the output current I_OUTfor charging the battery is greater than a predetermined threshold (e.g., when a voltage drop on the sense resistor R₁is higher than a predetermined level (e.g., 50 mV)). In the example of FIG. 1, the sense resistor R₁is coupled between the inductor L and the capacitor C, so as to provide a current feedback indicating the inductor current I_L. In another embodiment, the sense resistor R₁can be coupled between the capacitor C and the output terminal 112, so as to provide a current feedback indicating the output current I_OUT. The controller 102 can sense the inductor current I_Lor the output current I_OUTvia the terminals CSN and CSP by an amplifier in the controller 102 and compare the sensed current with a current reference Iâ€²_REF. The current reference Iâ€²_REFcan be greater than the current reference I_REF. A duty cycle of the PWM signal controlling the switches Q₁and Q₂can be adjusted according to a result of the current comparison so as to adjust the output current I_OUTto the current reference Iâ€²_REF. In addition, the controller 102 can compare a feedback voltage V_FBat the terminal VFB with a target voltage V_TARGETat the terminal SLEW. The duty cycle of the PWM signal can also be adjusted according to a result of the voltage comparison so as to adjust the output voltage V_OUTto the target voltage V_TARGET.

In the small current charging mode (e.g., during wake-up charging, trickle charging, and end of charging, etc.), the output current I_OUTfor charging the battery is relatively small, e.g., less than a predetermined threshold. Advantageously, instead of sensing the current via the sense resistor R₁, the controller 102 can calculate or adjust durations T_ON, T_OFF, and T_SKIPbased on the current reference I_REF. Thus, the controller 102 can adjust the output current I_OUTto the current reference I_REF. For example, according to equation (9), if the on state duration T_ONis determined or fixed, by controlling the skip state duration T_SKIPto a certain value, e.g., by controlling an input signal at a terminal SKIP of the controller 102 or calculating/adjusting the T_SKIPby a timer delay circuit in the controller 102, the output current I_OUTcan be controlled to the current reference level I_REF.

FIG. 3 illustrates a block diagram example of a power converter 300, in accordance with another embodiment of the present invention. Elements that are labeled the same as in FIG. 1 have similar functions. As shown in FIG. 3, the high-side switch Q₁is coupled to ground via a conduction path. The conduction path can include a diode D₁having a P terminal coupled to the high-side switch Q₁and having an N terminal coupled to ground. In one such embodiment, the low-side switch Q₂in the example of FIG. 1 can be omitted.

In the example of FIG. 3, during the on state duration T_ON, the PWM signal can be logic high so as to turn on the high-side switch Q₁, and the diode D₁can be cut off. Meanwhile, the inductor current I_Lcan increase from zero to the peak current level I_PK. During the off state duration T_OFF, the PWM signal can be logic low so as to turn off the high-side switch Q₁. The diode D₁can be in conduction, and the inductor current I_Lcan flow through the diode D₁from ground to the inductor L. Meanwhile, the inductor current I_Lcan decrease from the peak current level I_PKto zero. During the skip state duration T_SKIP, the PWM signal can still be logic low. As such, the high-side switch Q₁and the diode D₁both can be cut off, and the inductor current I_Lcan be approximately zero. Similarly, according to equation (9), the output current I_OUTcan be adjusted properly by controlling the on state duration T_ONand the skip state duration T_SKIP.

FIG. 4 illustrates a block diagram example of part of the controller 102, in accordance with one embodiment of the present invention. FIG. 4 is described in combination with FIG. 1 and FIG. 3. As shown in FIG. 4, the controller 102 can provide a PWM control signal and an LDR_EN signal to the driver 104 (in FIG. 1), so as to control the high-side switch Q₁and the low-side switch Q₂. In one embodiment, the controller 102 can count blocks of time and provide the appropriate PWM control signal and the LDR_EN signal based on such counts.

For instance, the controller 102 can include a one-shot circuit 402, a one-shot circuit 404, a comparator 406, a time delay circuit 408, and a NOR gate 410. The one-shot circuit 402 can provide the PWM control signal and the one-shot circuit 404 can provide the LDR_EN signal. The one-shot circuits 402 and 404 can be triggered by falling edges of the input signals. For example, if the input signal at the terminal TRIG of the one-shot circuit 402 changes from logic high to logic low, the one-shot circuit 402 can output a PWM signal that is logic high for a time interval, e.g., an on state duration T_ON. When the time interval T_ONexpires, the PWM signal can change to logic low. Similarly, if the input signal at the terminal TRIG of the one-shot circuit 404 changes from logic high to logic low, the one-shot circuit 404 can output an LDR_EN signal that is logic high for a time interval, e.g., an off state duration T_OFF. When the time interval T_OFFexpires, the LDR_EN signal can change to logic low.

The time delay circuit 408 can be a blanking circuit for generating retriggering of the one-shot circuit 402. For example, the time delay circuit 408 can receive the PWM signal from the one-shot circuit 402, and can be reset by a falling edge of the PWM signal. If the PWM signal changes from logic high to logic low, a timer in the time delay circuit 408 can start to run. The time delay circuit 408 can output logic high to the NOR gate 410 when a time interval, e.g., an off state duration T_OFFplus a skip state duration T_SKIP(T_OFF+T_SKIP), expires. As such, the NOR gate 410 can output logic low to trigger the one-shot circuit 402. Moreover, the terminal TRIG of the one-shot circuit 404 can receive the PWM signal from the one-shot circuit 402. Thus, if the PWM signal changes from logic high to logic low, the one-shot circuit 404 can be triggered.

The comparator 406 can compare a feedback voltage V_FBat the terminal VFB of the controller 102 and a target voltage V_TARGETat the terminal SLEW of the controller 102, so as to generate an output signal to the NOR gate 410. In one embodiment, if the feedback voltage V_FBis no less than the target voltage V_TARGET, the output signal can be logic low. If the feedback voltage V_FBis less than the target voltage V_TARGET, the output signal can be logic high, such that the NOR gate 410 can output logic low to trigger the one-shot circuit 402. At this moment, the PWM signal can be logic high so as to turn on the high-side switch Q₁(in FIG. 1 and FIG. 3), and the output voltage V_OUTcan increase. Thus, the output voltage V_OUTcan be adjusted to the target voltage V_TARGET, in one embodiment.

In one embodiment, during the normal current charging mode as mentioned above, the controller 102 can enable the comparator 406 so as to adjust the output voltage V_OUTto the target voltage V_TARGET. During the small current charging mode, the controller 102 can disable the comparator 406, and adjust the output current I_OUTby controlling the on state duration T_ON, the off state duration T_OFFand the skip state duration T_SKIP.

In one embodiment, the controller 102 in FIG. 4 can be implemented in the power converter 100 in FIG. 1, so as to control the high-side switch Q₁and the low-side switch Q₂. In another embodiment, the controller 102 in FIG. 4 can also be implemented in the power converter 300 in FIG. 3, so as to control the high-side switch Q₁and the diode D₁. In one such embodiment, the output terminal Q of the one-shot circuit 404 can be left floating.

FIG. 5 illustrates plot examples of a first control signal (the PWM signal), a second control signal (the LDR_EN signal) and the inductor current I_L, in accordance with one embodiment of the present invention. FIG. 5 is described in combination with FIG. 4.

As shown in FIG. 5, plots 502 and 504 respectively show the waveforms of the PWM signal and the LDR_EN signal. When the one-shot circuit 402 is triggered, the PWM signal can be logic high for a time interval T_ON. During the time interval T_ON, the inductor current I_Lcan increase. When the PWM signal changes from logic high to logic low, the one-shot circuit 404 can be triggered and the time delay circuit 408 can be reset. For example, the LDR_EN signal can change from logic low to logic high and last for a time interval T_OFF, and then change to logic low when the time interval T_OFFexpires. During the time interval T_OFF, the inductor current I_Lcan decrease. The time delay circuit 408 can be reset and start to count the time. When a time interval T_OFF+T_SKIPexpires, the time delay circuit 408 can output logic high to trigger the one-shot circuit 402, so as to change the PWM signal to logic high. During the time interval T_SKIP, the inductor current I_Lcan be approximately zero.

FIG. 6 illustrates a flowchart 600 of examples of operations performed by a power converter 100/300, in accordance with one embodiment of the present invention. FIG. 6 is described in combination with FIG. 1, FIG. 2 and FIG. 3.

In blocks 602 and 604, the controller 102 can enable (turn on) the high-side switch Q₁and disable (cut off) a conduction path, e.g., the low-side switch Q₂or the diode D₁, that is coupled to the high-side switch Q₁during the on state duration T_ON. In blocks 606 and 608, the controller 102 can enable the conduction path D₁/Q₂, and disable the high-side switch Q₁during the off state duration T_OFF. In block 610, the controller 102 can disable the high-side switch Q₁and the conduction path D₁/Q₂during the skip state duration T_SKIP.

In block 612, the controller 102 can control the on state duration T_ONand the skip state duration T_SKIPbased on the current reference I_REF. For example, based on equation (9), the controller 102 can calculate the on state duration T_ONand/or the skip state duration T_SKIPbased on the current reference level I_REF.

In block 614, the controller 102 can generate a first control signal, e.g., the PWM signal, to control the high-side switch Q₁and the conduction path D₁/Q₂according to the on state duration T_ONand the skip state duration T_SKIP. As such, as described in block 616, the controller 102 can adjust the output current I_OUTof the power converter 100/300, e.g., the equivalent current I_L_â€”_EQV, to the current reference I_REFaccording to the first control signal.

Accordingly, embodiments according to the present invention provide a power converter that can adjust an output current in differently ways depending on the level of the output current. The power converter can be used in many applications, e.g., a battery charging system and a power supply system, etc. For example, the power converter can provide a supply current to a load, or a charging current to a battery. Advantageously, such power converter can control the supply/charging current to a relatively low level in a relatively accurate way.

While the foregoing description and drawings represent embodiments of the present invention, it will be understood that various additions, modifications and substitutions may be made therein without departing from the spirit and scope of the principles of the present invention as defined in the accompanying claims. One skilled in the art will appreciate that the invention may be used with many modifications of form, structure, arrangement, proportions, materials, elements, and components and otherwise, used in the practice of the invention, which are particularly adapted to specific environments and operative requirements without departing from the principles of the present invention. The presently disclosed embodiments are therefore to be considered in all respects as illustrative and not restrictive, the scope of the invention being indicated by the appended claims and their legal equivalents, and not limited to the foregoing description.